FUJITSU SEMICONDUCTOR DATA SHEET
DS04-27240-1E
ASSP for Power Supply Applications (Secondary Battery)
DC/DC Converter IC for Charging Li-ion Battery
MB39A113
s DESCRIPTION
MB39A113 is a DC/DC converter IC of pulse width modulation (PWM) type for charging, capable of independently controlling the output voltage and output current. MB39A113 is suitable for down conversion. MB39A113 can dynamically control the charge current of the secondary battery, to keep the power constant by detecting a voltage drop in an AC adapter (dynamically-controlled charging) . MB39A113 can easily set the charge current value, making it ideal for use as a built-in charging device in products such as notebook PC.
s FEATURES
* Built-in dual constant-current control circuits * Analog control of charge current is possible. (+INE1 and +INE2 terminals) * Built-in AC adapter detection function (fixing the output in the off state when the VCC voltage is lower than the battery voltage + 0.2 V) * Possible to prevent mis-detecting of fully-charged state by constant-voltage control state detection function (CVM terminal) * Built-in overvoltage detection function of charge-voltage (OVP terminal) (Continued)
s PACKAGE
24-pin plastic SSOP
(FPT-24P-M03)
MB39A113
(Continued) * Wide range of operating power-supply voltage : 8 V to 25 V * Output voltage setting accuracy : 0.74% (Ta = -10 C to + 85 C) * Built-in high accuracy current detection amplifier : 5% (At the input voltage difference of 100 mV) , 15% (At the input voltage difference of 20 mV) * Output voltage setting resistor is open to enable prevention of invalidity current at IC standby. (ICC = 0 A Typ) * Oscillation frequency range : 100 kHz to 500 kHz * Built-in current detection amplifier with wide in-phase input voltage range : 0 V to VCC * Built-in soft-start function independent of loads * Built-in standby current function : 0 A (Typ) * Built-in totem-pole output stage supporting P-channel MOS FETs devices
2
MB39A113
s PIN ASSIGNMENT
(TOP VIEW)
-INC2 OUTC2 +INE2 -INE2 CVM +INC2 GND
1
24
2
23
3
22
CS
4
21
VCC
5
20
OUT
VREF
6
19
VH
FB12 -INE1 +INE1 OUTC1
7
18
OVP
8
17
RT -INE3 FB3
9
16
10
15
OUTD -INC1
11
14
CTL +INC1
12
13
(FPT-24P-M03)
3
MB39A113
s PIN DESCRIPTION
Pin No. 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 Symbol -INC2 OUTC2 + INE2 -INE2 CVM VREF FB12 -INE1 + INE1 OUTC1 OUTD -INC1 + INC1 CTL FB3 -INE3 RT OVP VH OUT VCC CS GND + INC2 I/O I O I I O O O I I O O I I I O I O O O I Description Current detection amplifier (Current Amp2) inverted input terminal Current detection amplifier (Current Amp2) output terminal Error amplifier (Error Amp2) non-inverted input terminal Error amplifier (Error Amp2) inverted input terminal Open drain type output terminal of constant-voltage control state detection comparator (CV Comp.) Reference voltage output terminal Error amplifier (Error Amp1, Error Amp2) output terminal Error amplifier (Error Amp1) inverted input terminal Error amplifier (Error Amp1) non-inverted input terminal Current detection amplifier (Current Amp1) output terminal With IC in standby mode, this terminal is set to Hi-Z to prevent loss of current through output voltage setting resistance. CTL terminal : Output "L" level at "H" level Current detection amplifier (Current Amp1) inverted input terminal Current detection amplifier (Current Amp1) non-inverted input terminal Power supply control terminal Setting the CTL terminal at "L" level places the IC in the standby mode. Error amplifier (Error Amp3) output terminal Error amplifier (Error Amp3) inverted input terminal Triangular wave oscillation frequency setting resistor connection terminal Open drain type output terminal of overvoltage detection comparator (OVComp.) Power supply terminal for FET drive circuit. (VH = VCC-6 V) External FET gate drive terminal. Power supply terminal for reference power supply control circuit and output circuit Soft-start capacitor connection terminal Ground terminal Current detection amplifier (Current Amp2) non-inverted input terminal
4
MB39A113
s BLOCK DIAGRAM
5 CVM
- + -INE1 8 VREF - + + 0.2 V + -INE2 4 + x20 - - + + -INC2 (VO) + + - - + - 1.4 V 2.6 V + x20 -
OUTC1 +INC1 -INC1
10 13 12
18 OVP
+INE1
9
OUTC2 +INC2 -INC2 +INE2 FB12
2 24 1 3
21
VCC
Drive 20 OUT
7 VREF -2.5 V VH Bias Voltage VCC - 6 V -1.5 V 19 VH
-INE3 OUTD
16 11
- + + 4.2 V
UVLO VREF UVLO
FB3
15
VREF 10 A 500 kHz CS 22 CT 45 pF 17 RT 6 VREF VREF 5.0 V 23 GND [ 4.2 V bias VCC]
14
CTL
5
MB39A113
s ABSOLUTE MAXIMUM RATINGS
Parameter Power supply voltage Output current Peak output current Power dissipation Storage temperature Symbol VCC IOUT IOUT PD TSTG Conditions VCC terminal Duty 5% (t = 1/fosc x Duty) Ta +25 C Rating Min -55 Max 28 60 700 740* +125 Unit V mA mA mW C
* : The package are mounted on the dual-sided epoxy board (10 cm x 10 cm) . WARNING: Semiconductor devices can be permanently damaged by application of stress (voltage, current, temperature, etc.) in excess of absolute maximum ratings. Do not exceed these ratings.
s RECOMMENDED OPERATING CONDITIONS
Min 8 Power supply voltage VCC VCC terminal -1 Reference voltage output current IREF 0 VH terminal output current IVH 0 VINE -INE1 to -INE3, + INE1, + INE2 terminal Input voltage 0 VINC + INC1, + INC2, -INC1, -INC2 terminal 0 CTL terminal input voltage VCTL -45 Output current IOUT -600 Peak output current IOUT Duty 5% (t = 1/fosc x Duty) 0 CVM terminal output voltage VCVM 0 CVM terminal output current ICVM 0 OVP terminal output voltage VOVP OVP terminal output current IOVP 0 OUTD terminal output voltage VOUTD 0 0 OUTD terminal output current IOUTD Oscillation frequency fosc 100 Timing resistor RT 27 Soft-start capacitor CS VH terminal capacitor CVH Reference voltage output capacitor CREF Operating ambient temperature Ta -30 Parameter Symbol Conditions Value Typ 300 47 0.022 0.1 0.1 +25 Max 25 0 30 5 VCC 25 +45 +600 25 1 25 1 17 2 500 130 1.0 1.0 1.0 +85 Unit V mA mA V V V mA mA V mA V mA V mA kHz k F F F C
WARNING: The recommended operating conditions are required in order to ensure the normal operation of the semiconductor device. All of the device's electrical characteristics are warranted when the device is operated within these ranges. Always use semiconductor devices within their recommended operating condition ranges. Operation outside these ranges may adversely affect reliability and could result in device failure. No warranty is made with respect to uses, operating conditions, or combinations not represented on the data sheet. Users considering application outside the listed conditions are advised to contact their FUJITSU representatives beforehand.
6
MB39A113
s ELECTRICAL CHARACTERISTICS
(VCC = 19 V, VREF = 0 mA, Ta = +25 C) Parameter Output voltage Reference Voltage Block [REF] Input stability Load stability Short-circuit output current UnderVoltage (VCC) Lockout Protection Circuit Block [UVLO] Soft-start Block [SOFT] Triangular Wave Oscillator Block [OSC] Threshold voltage VTHL Hysteresis width Charge current Oscillation frequency Frequency temperature stability Input offset voltage Input bias current Error Amplifier Block [Error Amp1, Error Amp2] Voltage gain Frequency bandwidth Output voltage Output source current Output sink current * : Standard design value VH ICS fosc f/fdt VIO IB AV BW VFBH VFBL ISOURCE ISINK 6 6 22 20 20 3, 4, 8, 9 3, 4, 8, 9 7 7 7 7 7 7 DC AV = 0 dB FB12 = 2 V FB12 = 2 V VREF = RT = 47 k Ta = -30 C to + 85 C FB12 = 2 V 2.4 -14 270 -100 4.8 2.0 2.6 0.2* -10 300 1* 1 -30 100* 1.3* 5.0 0.8 -120 4.0 2.8 -6 330 5 0.9 -60 V V A kHz % mV nA dB MHz V V A mA Symbol VREF1 VREF2 Line Load Ios VTLH Pin No. 6 6 6 6 6 6 Conditions Ta = +25 C Ta = -10 C to +85 C VCC = 8 V to 25 V VREF = 0 mA to -1 mA VREF = 1 V VREF = Value Min Typ Max 4.975 5.000 5.025 4.963 5.000 5.037 -50 2.6 3 1 -25 2.8 10 10 -12 3.0 Unit V V mV mV mA V
(Continued)
7
MB39A113
(VCC = 19 V, VREF = 0 mA, Ta = +25 C) Parameter Input current Voltage gain Frequency bandwidth Symbol Pin No. 16 15 15 15 15 15 15 16 16 11 11 Conditions -INE3 = 0 V DC AV = 0 dB FB3 = 2 V FB3 = 2 V FB3 = 2 V, Ta = + 25 C FB3 = 2 V, Ta = -10 C to + 85 C OUTD = 17 V OUTD = 1 mA Value Unit Min Typ Max -100 -30 nA 100* dB 1.3* MHz 4.8 5.0 V 0.8 0.9 V -120 -60 A 2.0 4.0 mA 4.179 4.200 4.221 V 4.169 4.200 4.231 0 35 1 50 +3 30 0.2 2.1 0.46 2.2 0.6 VCC 21 200 -1 V A mV A A A A V V V V V V/V MHz V mV mA A
IINE AV BW VFBH Output voltage VFBL Error Output source current ISOURCE Amplifier Output sink current ISINK Block VTH1 [Error Amp3] Threshold voltage VTH2 OUTD terminal output leak current OUTD terminal output ON resistor Input offset voltage ILEAK RON VIO I+INCH I-INCH Input current I+INCL I-INCL Current Detection Amplifier Block [Current Amp1, Current Amp2] VOUTC1 Current detection voltage VOUTC2 VOUTC3 VOUTC4 In-phase input voltage range Voltage gain Frequency bandwidth VCM AV
BW VOUTCH Output voltage VOUTCL Output source current ISOURCE Output sink current ISINK * : Standard design value
1, 12, + INC1 = + INC2 = -3 13, 24 -INC1 = -INC2 = 3 V to VCC + INC1 = + INC2 = 3 V to VCC, 13, 24 20 VIN = -100 mV + INC1 = + INC2 = 3 V to VCC, 1, 12 0.1 VIN = -100 mV + INC1 = + INC2 = 0 V, 13, 24 -180 -120 VIN = -100 mV + INC1 = + INC2 = 0 V, 1, 12 -195 -130 VIN = -100 mV + INC1 = + INC2 = 3 V to VCC, 2, 10 1.9 2.0 VIN = -100 mV + INC1 = + INC2 = 3 V to VCC, 2, 10 0.34 0.40 VIN = -20 mV + INC1 = + INC2 = 0 V, 2, 10 1.8 2.0 VIN = -100 mV + INC1 = + INC2 = 0 V, 2, 10 0.2 0.4 VIN = -20 mV 1, 12, 0 13, 24 + INC1 = + INC2 = 3 V to VCC, 2, 10 19 20 VIN = -100 mV 2, 10 AV = 0 dB 2* 2, 10 4.7 4.9 2, 10 20 2, 10 OUTC1 = OUTC2 = 2 V -2 2, 10 OUTC1 = OUTC2 = 2 V 150 300
(Continued)
8
MB39A113
(Continued)
Parameter PWM Comparator Block [PWM Comp.] Symbol VTL Threshold voltage Output source current Output sink current Output Block [OUT] Output ON resistor Rise time Fall time AC Adaptor Detection Block [UV Comp.] Threshold voltage Hysteresis width Threshold voltage Constant-voltage Hysteresis width Control State Detection Block CVM terminal output leakage current [CV Comp.] CVM terminal output ON resistor Threshold voltage Overvoltage Detection Block [OV Comp.] Hysteresis width OVP terminal output leak current OVP terminal output ON resistor CTL input voltage Control Block [CTL] Input current Bias Voltage Block [VH] General VTH ISOURCE ISINK ROH ROL tr1 tf1 VTLH VTHL VH VTLH VTHL VH ILEAK RON VTLH VTHL VH ILEAK RON VON VOFF ICTLH ICTLL VH ICCS ICC Pin No. (VCC = 19 V, VREF = 0 mA, Ta = +25 C) Conditions Value Min 1.4 16.8 2.6 2.5 CVM = 25 V CVM = 1 mA FB3 = FB3 = OVP = 25 V OVP = 1 mA IC operation mode IC standby mode CTL = 5 V CTL = 0 V VCC = 8 V to 25 V, VH = 0 mA to 30 mA CTL = 0 V CTL = 5 V 1.3 1.2 2 0 VCC -6.5 Typ 1.5 2.5 -400* 400* 6.5 5.0 50* 50* 17.4 17.0 0.4* 2.7 2.6 0.1* 0 200 1.4 1.3 0.1* 0 200 100 0 VCC -6.0 0 5 Max 2.6 9.8 7.5 17.6 17.2 2.8 2.7 1 400 1.5 1.4 1 400 25 0.8 150 1 VCC -5.5 10 7.5 Unit V V mA mA ns ns V V V V V V A V V V A V V A A V A mA
7, 15 Duty cycle = 0% 7, 15 Duty cycle = 100% 20 20 20 20 20 20 21 21 21 5 5 5 5 5 18 18 18 18 18 14 14 14 14 19 21 21 FB3 = FB3 = OUT = 13 V, Duty 5% (t = 1/fosc x Duty) OUT = 19 V, Duty 5% (t = 1/fosc x Duty) OUT = -45 mA OUT = 45 mA OUT = 3300 pF OUT = 3300 pF VCC = VCC = , -INC2 = 16.8 V
, -INC2 = 16.8 V 17.2
Output voltage Standby current Power supply current
* : Standard design value 9
MB39A113
s TYPICAL CHARACTERISTICS
Power Supply Current vs. Power Supply Voltage Power supply current ICC (mA)
6 5 4 3 2 1 0 0 5 10 15 Ta = +25 C CTL = 5 V 20 25
CTL terminal input current ICTL (A)
CTL Terminal Input Current, Reference Voltage vs. CTL Terminal Input Voltage
1000 900 800 700 600 500 400 300 200 100 0 0 5
VREF
ICTL
10
15
20
25
Power supply voltage VCC (V)
CTL terminal input voltage VCTL (V)
Reference Voltage vs. Power Supply Voltage
6 6
Reference Voltage vs. Load Current Reference voltage VREF (V)
Ta = +25 C VCC = 19 V CTL = 5 V
Reference voltage VREF (V)
5 4 3 2 1 0 0 5 10 15 20 25 Ta = +25 C CTL = 5 V VREF = 0 mA
5 4 3 2 1 0 0 5 10 15 20
25
30
35
Power supply voltage VCC (V)
Load current IREF (mA)
Reference Voltage vs. Operating Ambient Temperature Triangular wave oscillation frequency fosc (kHz) Reference voltage VREF (V)
5.08 5.06 5.04 5.02 5.00 4.98 4.96 4.94 4.92 -40 -20 0 20 40 60 80 100 340 330 320 310 300 290 280 270 260 VCC = 19 V CTL = 5 V VREF = 0 mA
Triangular Wave Oscillation Frequency vs. Power Supply Voltage
Ta = +25 C CTL = 5 V RT = 47 k
Operating ambient temperature Ta ( C)
0
5
10
15
20
Power supply voltage VCC (V)
(Continued)
10
Reference voltage VREF (V)
25
Ta = +25 C VCC = 19 V VREF = 0 mA
10 9 8 7 6 5 4 3 2 1 0
MB39A113
Triangular Wave Oscillation Frequency vs. Operating Ambient Temperature Triangular wave oscillation frequency fosc (kHz)
340 330 320 310 300 290 280 270 260 -40 -20 0 20 40 60 80 100 VCC = 19 V CTL = 5 V RT = 47 k
Triangular Wave Oscillation Frequency vs. Timing Resistor Triangular wave oscillation frequency fosc (kHz)
1000
Ta = +25 C VCC = 19 V CTL = 5 V
100
Operating ambient temperature Ta ( C)
10 10
100
1000
Timing resistor RT (k)
Error Amplifier Threshold Voltage vs. Operating Ambient Temperature Error amplifier threshold voltage VTH (V)
4.25 4.24 4.23 4.22 4.21 4.20 4.19 4.18 4.17 4.16 4.15 -40 -20 0 20 40 60 80 100 VCC = 19 V CTL = 5 V
Operating ambient temperature Ta ( C)
(Continued)
11
MB39A113
Error Amplifier, Gain and Phase vs. Frequency
40 30 20 Ta = +25 C VCC = 19 V 180 240 k
Gain AV (dB)
AV
90
Phase (deg)
10 0 -10 -20 -30 -40 100 1k 10 k 100 k 1M -180 10 M -90 0
10 k 1 F IN 8 2.4 k (4) 9 10 k (3)
+
- + + CS 7 OUT Error Amp1 (Error Amp2)
Frequency f (Hz) Error Amplifier, Gain and Phase vs. Frequency
40 30 20 90 240 k Ta = +25 C VCC = 19 V 180
Gain AV (dB)
Phase (deg)
10 0 -10 -20 -30 -40 100 1k 10 k 100 k 1M -180 10 M -90 AV 0
10 k 1 F
+
16 2.4 k
- + + 4.2 V 15 OUT Error Amp3
IN 10 k
CS
Frequency f (Hz) Current Detection Amplifier, Gain and Phase vs. Frequency
40 30 20 AV 90 180
Gain AV (dB)
Phase (deg)
10 0 -10 -20 -30 -40 100 1k 10 k 100 k 1M -180 10 M -90 0
10 k 1 F
+
VCC = 19 V 13 + (24) 12 - (1)
IN 10 k
10 (2) OUT
12.6 V Current Amp1 (Current Amp2)
Frequency f (Hz)
(Continued)
12
MB39A113
(Continued)
Power Dissipation vs. Operating Ambient Temperature
800 740 700 600 500 400 300 200 100 0 -40 -20 0 20 40 60 80 100
Power dissipation PD (mW)
Operating ambient temperature Ta ( C)
13
MB39A113
s FUNCTIONAL DESCRIPTION
1. DC/DC Converter Block
(1) Reference voltage block (REF) The reference voltage circuit generates a temperature-compensated reference voltage (5.0 V Typ) using the voltage supplied from the VCC terminal (pin 21) . The voltage is used as the reference voltage for the IC's internal circuit. The reference voltage can be used to supply a load current of up to 1 mA to an external device through the VREF terminal (pin 6) . (2) Triangular wave oscillator block (OSC) The triangular wave oscillator block has built-in a frequency setting capacitor, and generates the triangular wave oscillation waveforms by connecting the frequency setting resistor with the RT terminal (pin 17) . The triangular wave is input to the IC's internal PWM comparator. (3) Error amplifier block (Error Amp1) The error amplifier (Error Amp1) detects voltage drop of the AC adaptor and a PWM control signal is output. By connecting a feedback resistor and capacitor between FB12 terminal (pin 7) and -INE1 terminal (pin 8) , it is possible to create any desired level of loop gain, thereby providing stable phase compensation to the system. Also, it is possible to prevent rush current at power supply start-up by connecting a soft-start capacitor with the CS terminal (pin 22) . The use of error amplifier for soft-start detection makes it possible for a system to operate on a fixed soft-start time that is independent of the output load. (4) Error amplifier block (Error Amp2) The error amplifier detects output signal of current detection amplifier (Current Amp2) and outputs PWM control signal by comparison with +INE2 terminal (pin 3) , also controls charge current. By connecting a feedback resistor and capacitor between FB12 terminal (pin 7) and -INE2 terminal (pin 4) , it is possible to create any desired level of loop gain, thereby providing stable phase compensation to the system. Also, it is possible to prevent rush current at power supply start-up by connecting a soft-start capacitor with the CS terminal (pin 22) . The use of error amplifier for soft-start detection makes it possible for a system to operate on a fixed soft-start time that is independent of the output load. (5) Error amplifier block (Error Amp3) The error amplifier (Error Amp3) detects the DC/DC converter output voltage and outputs PWM control signals. An arbitrary output voltage can be set for 1 to 4 cells by connecting external output voltage setting resistors to the error amplifier inverting input pins. By connecting a feedback resistor and capacitor between FB3 terminal (pin15) and -INE3 terminal (pin 16) , it is possible to create any desired level of loop gain, thereby providing stable phase compensation to the system. Also, it is possible to prevent rush current at power supply start-up by connecting a soft-start capacitor with the CS terminal (pin 22) . The use of error amplifier for soft-start detection makes it possible for a system to operate on a fixed soft-start time that is independent of the output load.
14
MB39A113
(6) Current detection amplifier block (Current Amp1) The current detection amplifier (Current Amp1) detects voltage drop which occurs between both ends of the output sense resistor (RS) due to the flow of the charge current, using the +INC1 terminal (pin 13) and -INC1 terminal (pin 12) . Then it outputs the signal amplifier by 20 times to the error amplifier (Error Amp1) at the next stage. (7) Current detection amplifier block (Current Amp2) The current detection amplifier (Current Amp2) detects voltage drop which occurs between both ends of the output sense resistor (RS) due to the flow of the charge current, using the +INC2 terminal (pin 24) and -INC2 terminal (pin 1) . Then it outputs the signal amplified by 20 times to the error amplifier (Error Amp2) at the next stage. (8) PWM comparator block (PWM Comp.) The PWM comparator circuit is a voltage-to-pulse width modulator that controls the output duty depending on the output voltage of error amplifier (Error Amp1 to Error Amp3) . The PWM comparator circuit compares the triangular wave generated by the triangular wave oscillator to the error amplifier output voltage and turns on the external output transistor during the interval in which the triangular wave voltage is lower than the error amplifier output voltage. (9) Output block (OUT) The output circuit uses a totem-pole configuration capable of driving an external P-channel MOS FET. The output "L" level sets the output amplitude to 6 V (Typ) using the voltage generated by the bias voltage block (VH) . This results in increasing conversion efficiency and suppressing the withstand voltage of the connected external transistor in a wide range of input voltages. (10) Power supply control block (CTL) Setting the CTL terminal (pin 14) low places the IC in the standby mode. (The supply current is 10 A at maximum in the standby mode.) CTL function table CTL Power L H OFF (Standby) ON (Active)
(11) Bias voltage block (VH) The bias voltage circuit outputs VCC-6 V (Typ) as the minimum potential of the output circuit. In the standby mode, this circuit outputs the potential equal to VCC.
15
MB39A113
2. Protection Functions
(1) Under-voltage lockout protection circuit (UVLO) The transient state of when the power supply (VCC) is turned on or a momentary decrease in supply voltage/ internal reference voltage (VREF) may cause malfunctions in the control IC, resulting in breakdown or degradation of the system. To prevent such malfunctions, the under-voltage lockout protection circuit detects an internal reference voltage drop and fixes OUT terminal (pin 20) to "H" level. The system restores when the internal reference voltage reaches the threshold voltage of the under-voltage lockout protection circuit. Protection circuit (UVLO) operation function table At UVLO operating (VREF voltage is lower than UVLO threshold voltage.) OUTD OUT CS CVM Hi-Z H L H
OVP H
(2) AC adapter detection block (UV Comp.) This block detects that power-supply voltage (VCC) is lower than the battery voltage + 0.2 V (Typ) , and the OUT terminal (pin 18) fixed at the "H" level. The system restores voltage supply when the supply voltage reaches the threshold voltage of the AC adapter detection block. Protection circuit (UV Comp.) operation function table At UV Comp. operating (VCC voltage is lower than UV Comp. threshold voltage.) OUTD OUT CS L H L
3. Soft-start Function
Soft-start block (SOFT) Connecting a capacitor to the CS terminal (pin 22) prevents rush currents from flowing upon activation of the power supply. Using the error amplifier to detect a soft-start allows to soft-start at constant setting time intervals independent of the output load of the DC/DC converter.
4. Detection Function
(1) Constant-voltage control state detection block (CV Comp.) Error amplifier (Error Amp3) detects the voltage at FB3 (pin 15) falling to or below 2.6 V (Typ) and outputs "L" level to the constant-voltage control state detection block output terminal (CVM, pin 5). (2) Overvoltage detection block (OV Comp.) Error amplifier (Error Amp3) detects the voltage at FB3 (pin 15) falling to or below 1.3 V (Typ) and outputs "H" level to the overvoltage detection block output terminal (OVP pin 18). ,
16
MB39A113
s SETTING THE CHARGING VOLTAGE
The charge voltage (DC/DC output voltage) can be set by connecting an external output voltage setting resistors (R3, R4) to the -INE3 terminal (pin 16) . Select a resistor value at which the on-resistor (35 at 1 mA) of the built-in FET connected to the OUTD terminal (pin 11) can be ignored. Charge voltage of battery : VO VO (V) = (R3 + R4) /R4 x 4.2 (V)
B VO
R3 -INE3 16 R4 11 OUTD
- + + 4.2 V
22 CS
s SETTING THE CHARGING CURRENT
The charge current value (output limit current) can be set depending on the voltage value at the +INE2 terminal (pin 3) . If a current exceeding the set current value attempts to flow, the charge voltage drops according to the set current value. Battery charge current setting voltage : + INE2 + INE2 (V) = 20 x I1 (A) x RS ()
s SETTING THE TRIANGULAR WAVE OSCILLATION FREQUENCY
The triangular wave oscillation frequency is determined by the timing resistor (RT) connected to the RT terminal (pin 17) . Triangular wave oscillation frequency : fosc fosc (kHz) = 14100/RT (k) :
17
MB39A113
s SETTING OF SOFT-START TIME
(1) Setting constant voltage mode soft-start To prevent rush currents when the IC is turned on, the IC allows soft-start using the capacitor (CS) connected to the CS terminal (pin 22) . When the CTL terminal (pin 14) is placed under "H" level and IC is activated (threshold voltage of VCC UVLO) , and Q2 is turned off and the external soft-start capacitor (CS) connected to the CS terminal is charged at 10 A. The Error Amp output potential (FB3 terminal (pin 15)) is determined through comparison between either of the lower potentials at two non-inverting input terminals (internal reference voltage (4.2 V Typ) , CS terminal voltage), and the inverting input terminal voltage ( - INE3 terminal (pin 16)) . Within the soft-start period (CS terminal voltage < 4.2 V) , FB3 is determined by comparison between - INE3 terminal voltage and CS terminal voltage, and DC/DC converter output voltage goes up proportionately with the increase of CS terminal voltage caused by charging on the soft-start capacitor. The soft-start time is obtained from the following formula. Soft-start time : ts (time until output voltage 100%) ts (s) = 0.42 x CS (F) : = 4.9 V : = 4.2 V : CS terminal voltage Error Amp block internal reference voltage
=0V :
Soft-start time : ts
VREF
10 A
10 A
FB3 15 -INE3 16 CS 22 - + + 4.2 V CS Q2
Error Amp3
UVLO
Soft-start circuit 18
MB39A113
(2) Setting constant current mode soft-start To prevent rush currents when the IC is turned on, the IC allows soft-start using the capacitor (CS) connected to the CS terminal (pin 22) . When the CTL terminal (pin 14) is placed under "H" level and IC is activated (threshold voltage of VREF UVLO) , and Q2 is turned off and the external soft-start capacitor (CS) connected to the CS terminal is charged at 10 A. The Error Amp1 output potential (FB12 terminal (pin 7) ) is determined through comparison between either of the lower potentials at two non-inverting input terminals ( + INE1 terminal (pin 9) voltage and CS terminal voltage), and the inverting input terminal voltage ( - INE1 terminal (pin 8) ) . Within the soft-start period (CS terminal voltage < + INE1) , FB12 is determined by comparison between - INE1 terminal voltage and CS terminal voltage, and DC/DC converter output voltage goes up proportionately with the increase of CS terminal voltage caused by charging on the soft-start capacitor. The Error Amp1 output potential (FB12 terminal (pin 7) ) is determined through comparison between either of the potentials at two non-inverting input terminals ( + INE2 terminal (pin 3) ) voltage and CS terminal voltage), and the inverting input terminal voltage ( - INE2 terminal (pin 4) ) . Within the soft-start period (CS terminal voltage < + INE2) , FB12 is determined by comparison between - INE2 terminal voltage and CS terminal voltage, and DC/DC converter output voltage goes up proportionately with the increase of CS terminal voltage caused by charging on the soft-start capacitor. The soft-start time is obtained from the following formula. Soft-start time : ts (time until output voltage 100%) ts (s) = + INE1 ( + INE2) /10 A x CS (F) : = 4.9 V : + INE1 ( + INE2) =0V : CS terminal voltage Error Amp1 block Comparison voltage with -INE1 voltage (Error Amp2 block Comparison voltage with -INE2 voltage)
Soft-start time : ts
19
MB39A113
VREF
10 A
10 A
FB12 -INE1 -INE2 CS +INE1 CS +INE2
7 Error Amp1 (Error Amp2) 8 4 22 9 3 Q2 UVLO - + +
Soft-start circuit
20
MB39A113
s SETTING THE DYNAMICALLY-CONTROLLED CHARGING
With an external resistor connected to + INE1(pin 9), the IC enters the dynamically-controlled charging mode to reduce the charge current to keep AC adapter power constant when the partial potential point A of the AC adapter voltage (VCC) become lower the - INE2 terminal voltage. Dynamically-controlled charging setting voltage : Vth Vth (V) = (R1 + R2) /R2 x -INE1
-INE1 A R1 R2 +INE1
8 9 - +
VCC
s ABOUT CONSTANT-VOLTAGE CONTROL STATE DETECTION/OVERVOLTAGE DETECTION TIMING CHART
In the constant-voltage control state, the CVM terminal (pin 5) of the constant-voltage control state detection block (CV Comp.) outputs "L" level, when the voltage at the FB3 terminal (pin 15) of the error amplifier (ErrorAmp 3) becomes 2.6 V (Typ) or less. When the DC/DC converter output voltage enters the state of the over-voltage higher than a setting voltage, the voltage at FB3 terminal (pin 15) of the error amplifier (Error Amp3) becomes 1.3 V (Typ) or less. As a result, the OVP terminal (pin 18) of the overvoltage detection block (OV Comp.) outputs "H" level. Both the CVM terminal and the OVP terminal are open-drain output forms :
Error Amp3 FB3 2.6 V CV Comp. VTHL 2.5 V
Error Amp2 Error Amp1 FB12 1.5 V 1.3 V OV Comp. VTHL CV Comp. CVM
OV Comp. OVP OUT
Constant current control
Constant voltage control
Overvoltage state 21
MB39A113
s ABOUT THE OPERATION TIMING CHART
Error Amp2 Error Amp1 FB12
2.5V
Error Amp3 FB3 1.5 V Current Amp2 OUTC2
OUT
Constant voltage control
Constant current control
AC adaptor dynamicallycontrolled charging
22
MB39A113
s PROCESSING WITHOUT USING OF THE CURRENT AMP1 AND AMP2
When Current Amp is not used, connect the +INC1 terminal (pin 13), +INC2 terminal (pin 24), -INC1 terminal (pin 12), and -INC2 terminal (pin 1) to VREF, and open the OUTC1 terminal (pin 10) and OUTC2 terminal (pin 2). * Connection when Current Amp is not used
-INC1 -INC2 OUTC1 OUTC2 +INC1 +INC2
12 1 10
13 24
"Open"
2
6
VREF
s PROCESSING WITHOUT USING OF THE ERROR AMP1 AND AMP2
When Error Amp is not used, leave the FB12 terminal (pin 7) open and connect the -INE1 terminal (pin 8) and -INE2 terminal (pin 4) to GND, and connect +INE1 terminal (pin 9) and +INE2 terminal (pin 3) to VREF. * Connection when Error Amp is not used
9 3 8 4
+INE1 +INE2 -INE1 -INE2
GND
23
"Open"
7 6 FB12 VREF
23
MB39A113
s PROCESSING WITHOUT USING OF THE CS TERMINAL
When soft-start function is not used, leave the CS terminal (pin 22) open. * When no soft-start function is specified
"Open"
CS 22
24
MB39A113
s I/O EQUIVALENT CIRCUIT
Reference voltage block
VCC 21 + - 6 VREF
Control block
CTL 14 37.8 k 12.35 k 33.1 k 51 k GND
ESD protection element
GND 23
ESD protection element
Soft-start block
VREF (5.0 V) VCC VREF (5.0 V) 22 CS
Triangular wave oscillator block
VCC
Error amplifier block (Error Amp1)
1.3 V
+ -
-INE1 8 17 RT CS
7 FB12
GND
GND GND 9 +INE1
Error amplifier block (Error Amp2)
VCC VREF (5.0 V) -INE2 4 CS FB12 VCC VREF (5.0 V)
Error amplifier block (Error Amp3)
-INE3 16
CS 4.2 V
15 FB3
GND 3 +INE2
GND
Current detection amplifier block (Current Amp1)
VCC VCC
Current detection amplifier block (Current Amp2)
+INC1 13 10 OUTC1
+INC2 24 2 OUTC2
GND 12 -INC1
GND 1 -INC2
(Continued)
25
MB39A113
(Continued)
PWM comparator block
VCC VCC
Output block
AC adaptor detection block
VCC -INC2
FB12 FB3
CT
20 OUT
VREF (5.0 V)
VH GND GND GND
Constant-voltage control state detection block
VCC VREF (5.0 V) FB3
VCC VREF (5.0 V)
Overvoltage detection block
5 CVM
18 OVP FB3
GND
GND
Bias voltage block
VCC
Prevent inefficient current block
11 OUTD
19 VH
GND
GND
26
MB39A113
s APPRICATION EXAMPLE
D2 VIN (8 V to 25 V) R4 180 k R5 330 k R6 30 k R10 120 k C8 10000 pF -INE1 5 CVM
- + 8 VREF - + + 0.2 V + 4 R8 100 k OUTC2 +INC2 2 24 1 +INE2 3 FB12 + x20 - - + + -INC2 (VO) + + - - + - 1.4 V 2.6 V + x20 -
R11 30 k
R7 22 k
OUTC1 +INC1 -INC1 10 13 12
18
OVP
+INE1 9 -INE2 C10 4700 pF R9 10 k A B R12 30 k
VCC 21 C12 0.1 F Drive 20 OUT Q1 I1 L1 R27 100 k VO Q3 C7 0.1 F C1 4.7 F C2 4.7 F A B
-INC2
R13 20 k R16 200 k Q2
SW
R14 1 k R15 120 R19 100 k R18 200 k
7 VREF VH -INE3 OUTD -2.5 V 16 11 4.2 V FB3 15 UVLO VREF UVLO - + + -1.5 V VH Bias Voltage VCC - 6 V 19 D1
15 H
+
R1 0.033 C4 4.7 F Battery
C3 22 F
C6 1500 pF R3 330 k
R17 100 k
VREF 10 A CS 22 C11 0.022 F CT 45 pF 17 RT R2 47 k VREF 6 GND VREF 5.0 V 23 500 kHz [ 4.2 V bias VCC CTL]
14
C9 0.1 F
27
MB39A113
s PARTS LIST
COMPONENT Q1, Q3 Q2 D1, D2 L1 C1, C2, C4 C3 C6 C7, C9 C8 C10 C11 C12 R1 R2 R3, R5 R4 R6 R7 R8 R9 R10 R11, R12 R13 R14 R15 R16, R18 R17, R19 R27 ITEM Pch FET Nch FET Diode Inductor Ceramics Condenser OS-CONTM Ceramics Condenser Ceramics Condenser Ceramics Condenser Ceramics Condenser Ceramics Condenser Ceramics Condenser Resistor Resistor Resistor Resistor Resistor Resistor Resistor Resistor Resistor Resistor Resistor Resistor Resistor Resistor Resistor Resistor SPECIFICATION VDS = -30 V, ID = -7.0 A VDS = 30 V, ID = 1.4 A VF = 0.42 V (Max) , At IF = 3 A 15 H 4.7 F 22 F 1500 pF 0.1 F 0.01 F 4700 pF 0.022 F 0.1 F 33 m 47 k 330 k 180 k 30 k 22 k 100 k 10 k 120 k 30 k 20 k 1 k 120 200 k 100 k 100 k 3.6 A, 50 m 25 V 20 V 50 V 50 V 50 V 50 V 50 V 50 V 1% 0.5% 0.5% 0.5% 0.5% 0.5% 0.5% 0.5% 0.5% 0.5% 0.5% 0.5% 0.5% 0.5% 0.5% 0.5% VENDOR NEC SANYO ROHM SUMIDA TDK SANYO TDK TDK TDK TDK TDK TDK KOA ssm ssm ssm ssm ssm ssm ssm ssm ssm ssm ssm ssm ssm ssm ssm PARTS No. PA2714GR MCH3401 RB053L-30 CDRH104R-150 C3225JB1E475K 20SVP22M C1608JB1H152K C1608JB1H104K C1608JB1H103K C1608JB1H472K C1608JB1H223K C1608JB1H104K SL1TTE33LOF RR0816P-473-D RR0816P-334-D RR0816P-184-D RR0816P-303-D RR0816P-223-D RR0816P-104-D RR0816P-103-D RR0816P-124-D RR0816P-303-D RR0816P-203-D RR0816P-102-D RR0816P-121-D RR0816P-204-D RR0816P-104-D RR0816P-104-D
Note : NEC : NEC Corporation SANYO : SANYO Electric Co., Ltd ROHM : ROHM CO., LTD. SUMIDA : Sumida Corporation TDK : TDK Corporation KOA : KOA Corporation ssm : SUSUMU CO., LTD OS-CON is a trademark of SANYO Electric Co., Ltd.
28
MB39A113
s SELECTION OF COMPONENTS
* Pch MOS FET The P-channel MOSFET for switching use should be rated for at least + 20% more than the input voltage. To minimize continuity loss, use a FET with low RDS (ON) between the drain and source. For high input voltage and high frequency operation, on-cycle switching loss will be higher so that power dissipation must be considered. In this application, the PA2714GR (NEC products) is used. Continuity loss, on/off switching loss and total loss are determined by the following formulas. The selection must ensure that peak drain current does not exceed rated values. Continuity loss : Pc PC = ID2 x RDS (ON) x Duty On-cycle switching loss : PS (ON) PS (ON) = VD (Max) x ID x tr x fosc 6
Off-cycle switching loss : PS (OFF) PS (OFF) = VD (Max) x ID (Max) x tf x fosc 6
Total loss : PT PT = PC + PS (ON) + PS (OFF) Example) Using the PA2714GR Setting 16.8 V Input voltage VIN = 25 V, output voltage VO = 16.8 V, drain current ID = 3 A, oscillation frequency fosc = 300 kHz, L = 15 H, drain-source ON resistance RDS (ON) = 18 m, tr = 15 ns, tf = 42 ns : : : Drain current (Max) : ID (Max) ID (Max) = Io + = 3+ = 3.6 A : Drain current (Min) : ID (Min) ID (Min) = Io - = 3- = 2.4 A : PC = ID2 x RDS (ON) x Duty = 32 x 0.018 x 0.672 = 0.109 W : 29 VIN-Vo 2L 25-16.8 2 x 15 x 10-6 tON x 1 300 x 103 x 0.672 VIN-Vo 2L 25-16.8 2 x 15 x 10
-6
tON x 1 300 x 103 x 0.672
MB39A113
VD x ID x tr x fosc 6 25 x 3 x 15 x 10-9 x 300 x 103 6
PS (ON) = =
= 0.056 W : PS (OFF) = = VD x ID (Max) x tf x fosc 6 25 x 3.6 x 42 x 10-9 x 300 x 103 6
= 0.189 W : PT = PC + PS (ON) + PS (OFF) = 0.109 + 0.056 + 0.189 : = 0.354 W : The above power dissipation figures for the PA2714GR are satisfied with ample margin at 2.0 W. Setting 12.6 V Input voltage VIN = 22 V, output voltage VO = 12.6 V, drain current ID = 3 A, oscillation frequency fosc = 300 kHz, L = 15 H, drain-source ON resistance RDS (ON) = 18 m, tr = 15 ns, tf = 42 ns : : : Drain current (Max) : ID (Max) ID (Max) = Io + = 3+ = 3.6 A : Drain current (Min) : ID (Min) ID (Min) = Io - = 3- = 2.4 A : PC = ID2 x RDS (ON) x Duty = 32 x 0.018 x 0.572 = 0.093 W : VIN-Vo 2L 22-12.6 2 x 15 x 10
-6
VIN-Vo 2L 22-12.6
tON x 1 300 x 103 x 0.572
2 x 15 x 10-6
tON x 1 300 x 103 x 0.572
30
MB39A113
VD x ID x tr x fosc 6 22 x 3 x 15 x 10-9 x 300 x 103 6 0.050 W VD x ID (Max) x tf x fosc 6 22 x 3.6 x 42 x 10-9 x 300 x 103 6
PS (ON) = = = : PS (OFF) = =
= 0.166 W : PT = PC + PS (ON) + PS (OFF) = : 0.093 + 0.050 + 0.166 = 0.309 W : The above power dissipation figures for the PA2714GR are satisfied with ample margin at 2.0 W. * Inductor In selecting inductors, it is of course essential not to apply more current than the rated capacity of the inductor, but also to note that the lower limit for ripple current is a critical point that if reached will cause discontinuous operation and a considerable drop in efficiency. This can be prevented by choosing a higher inductance value, which will enable continuous operation under light-load. Note that if the inductance value is too high, however, direct current resistance (DCR) is increased and this will also reduce efficiency. The inductance must be set at the point where efficiency is greatest. Note also that the DC superimposition characteristic becomes worse as the load current value approaches the rated current value of the inductor, so that the inductance value is reduced and ripple current increases, causing loss of efficiency. The selection of rated current value and inductance value will vary depending on where the point of peak efficiency lies with respect to load current. Inductance values are determined by the following formulas. The L value for all load current conditions is set so that the peak to peak value of the ripple current is 1/2 the load current or less. Inductance value : L L 2 (VIN-Vo) Io tON
16.8 V output Example) 2 (VIN (Max) -Vo) L Io 2 x (25-16.8) 3 12.2 H x
tON 1 300 x 103 x 0.672
31
MB39A113
12.6 V output Example) 2 (VIN (Max) -Vo) L Io 2 x (22-12.6) 3 x
tON 1 300 x 103 x 0.572
12.0 H Inductance values derived from the above formulas are values that provide sufficient margin for continuous operation at maximum load current, but at which continuous operation is not possible at light-loads. So, it is necessary to determine the load level at which continuous operation becomes possible. In this application, the SUMIDA CDRH104R-150 is used. The following equation is available to obtain the load current as a continuous current condition when 15 H is used. The load current value under continuous operating conditions : Io Io Vo 2L tOFF
Example) Using the CDRH104R-150 15 H (tolerance 30%) , rated current = 3.6 A 16.8 V output Vo Io tOFF 2L 16.8 2 x 15 x 10
-6
x
1 300 x 103
x
(1-0.672)
0.61 A 12.6 V output Vo Io tOFF 2L 12.6 2 x 15 x 10
-6
x
1 300 x 103
x
(1-0.572)
0.60 A To determine whether the current through the inductor is within rated values, it is necessary to determine the peak value of the ripple current as well as the peak-to-peak values of the ripple current that affect the output ripple voltage. The peak value and peak-to-peak value of the ripple current can be determined by the following formulas. Peak value : IL IL Io + VIN-Vo 2L tON
Peak-peak value : IL IL = VIN-Vo L tON
32
MB39A113
Example) Using the CDRH104R-150 15 H (tolerance 30%) , rated current = 3.6 A Peak value 16.8 V output IL Io + 3+ VIN-Vo 2L tON x 1 300 x 103 x 0.672
25-16.8 2 x 15 x 10
-6
3.6 A 12.6 V output IL Io + 3+ VIN-Vo 2L tON x 1 300 x 103 x 0.572
22-12.6 2 x 15 x 10
-6
3.6 A Peak-peak value 16.8 V output VIN-Vo IL = L = = : 25-16.8 15 x 10 1.22 A
-6
tON x 1 300 x 103 x 0.672
12.6 V output VIN-Vo IL = L 22-12.6 = 15 x 10-6 = 1.2 A : * Flyback diode
tON x 1 300 x 103 x 0.572
As a flyback diode, in general, a Schottky barrier diode (SBD) is used when the reverse voltage to the diode is 40 V or less. The SBD has the characteristic of higher speed in terms of faster reverse recovery time, and lower forward voltage, and is ideal for archiving high efficiency. There is no problem as long as the DC reverse voltage is sufficiently higher than the input voltage, and the mean current flowing during the diode conduction time is within the mean output current level, and as the peak current is within the peak surge current limits. In this application the RB053L-30 (ROHM) are used. The diode mean current and diode peak current can be obtained by the following formulas. Diode mean current : IDi Vo ) IDi Io x (1- VIN Diode peak current : IDip Vo IDip (Io + tOFF) 2L 33
MB39A113
Example) Using the RB053L-30 VR (DC reverse voltage) = 30 V, average output current = 3.0 A, peak surge current = 70 A VF (forward voltage) = 0.42 V, at IF = 3.0 A 16.8 V output IDi Io x Vo ) VIN 3 x (1-0.672) 0.984 A (1-
12.6 V output IDi Io x (1- Vo ) VIN 3 x (1-0.572) 1.284 A Vo 2L
16.8 V output IDip (Io + 3.6 A tOFF)
12.6 V output IDip (Io + 3.6 A Vo 2L tOFF)
* Smoothing capacitor The smoothing capacitor is an indispensable element for reducing ripple voltage in output. In selecting a smoothing capacitor, it is essential to consider equivalent series resistance (ESR) and allowable ripple current. Higher ESR means higher ripple voltage, so that to reduce ripple voltage it is necessary to select a capacitor with low ESR. Note, however, that the use of a capacitor with low ESR has substantial effects on loop phase characteristics, and impairing system stability. Care should also be taken to use a capacity with sufficient margin for allowable ripple current. In this application the 20SVP22M (OS-CONTM : SANYO) are used. The ESR, capacitance value, and ripple current can be obtained by the following formulas. Equivalent series resistance : ESR Vo 1 ESR - 2fCL IL Capacitance value : CL IL CL 2f (Vo-IL x ESR) Ripple current : ICLrms (VIN-Vo) tON ICLrms 23L
34
MB39A113
Example) Using the 20SVP22M Rated voltage = 20 V, ESR = 60 m, maximum allowable ripple current = 1450 mArms Equivalent series resistance 16.8 V output Vo 1 ESR - 2fCL IL 0.168 1.22 - 1 2 x 300 x 103 x 22 x 10-6
114 m
12.6 V output Vo ESR IL 0.126 1.2
- -
1 2fCL 1 2 x 300 x 103 x 22 x 10-6
80 m Capacitance value 16.8 V output CL IL 2f (Vo-IL x ESR) 1.22 2 x 300 x 10 x (0.168-1.22 x 0.06)
3
6.8 F 12.6 V output CL IL 2f (Vo-IL x ESR) 1.2 2 x 300 x 10 x (0.126-1.2 x 0.06)
3
11.8 F Ripple current 16.8 V output (VIN-Vo) tON ICLrms 23L (25-16.8) x 0.672 23 x 15 x 10-6 x 300 x 103 707 mArms
12.6 V output (VIN-Vo) tON ICLrms 23L (22-12.6) x 0.572 23 x 15 x 10-6 x 300 x 103
690 mArms 35
MB39A113
s REFERENCE DATA
Conversion Efficiency vs. Charge Current (constant voltage mode)
100 98 96
Efficiency (%)
94 92 90 88 86 84 82 80 0.01 0.1
Ta = + 25 C VAC = 19 V VBATT = 12.6 V setting = (VBATT x IBATT) / (VAC x IAC) Converted to VBATT
1
10
IBATT (A) Conversion Efficiency vs. Charge Voltage (constant current mode)
100 98 96
Efficiency (%)
94 92 90 88 86 84 82 80 0 2 4
Ta = + 25 C VAC = 19 V IBATT = 3 A setting = (VBATT x IBATT) / (VAC x IAC) Converted to VBATT
6
8
10
12
14
VBATT (V) BATT Voltage vs. BATT Charge Current (12.6 V setting)
18 16 14 12
Ta = + 25 C VAC = 19 V VBATT = 12.6 V setting
D.C.C. Mode Dead Battery Mode
VBATT (V)
10 8 6 4 2 0 0.0 0.5
D.C.C. Mode : Dynamically-controlled charging 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
IBATT (A)
(Continued)
36
MB39A113
Conversion Efficiency vs. Charge Current (constant voltage mode)
100 98 96
Efficiency (%)
94 92 90 88 86 84 82 80 0.01 0.1
Ta = + 25 C VAC = 19 V VBATT = 16.8 V setting = (VBATT x IBATT) / (VAC x IAC) Converted to VBATT
1
10
IBATT (A) Conversion Efficiency vs. Charge Voltage (constant current mode)
100 98 96
Efficiency (%)
94 92 90 88 86 84 82 80 0 2 4 6 8 10 12 14 16
Ta = + 25 C VAC = 19 V IBATT = 3 A setting = (VBATT x IBATT) / (VAC x IAC) Converted to VBATT
VBATT (V) BATT Voltage vs. BATT Charge Current (16.8 V setting)
18 16 14 12 D.C.C. Mode Dead Battery Mode
VBATT (V)
10 8 6 4 2 0 0.0 0.5
Ta = + 25 C VAC = 19 V VBATT = 16.8 V setting
D.C.C. Mode : Dynamically-controlled charging 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0
IBATT (A)
(Continued)
37
MB39A113
Switching Waveform at Constant Voltage Mode (12.6 V setting)
OUT(V) 15 VD(V) 20 15 10 5 0 VAC = 19 V CV mode IBATT = 1.5 A VBATT = 12.6 V setting 10 5 0
0
1
2
3
4
5
6
7
8
9
10 (s)
Switching Waveform at Constant Current Mode (12.6 V setting at 10 V)
OUT(V) 15 VAC = 19 V CC mode IBATT = 3 A setting VBATT = 10 V 10 5 0
VD(V) 20 15 10 5 0
0
1
2
3
4
5
6
7
8
9
10 (s)
(Continued)
38
MB39A113
Switching Waveform at Constant Voltage Mode (16.8 V setting)
OUT(V) 15 VAC = 19 V CV mode IBATT = 1.5 A VBATT = 16.8 V setting 10 5 0
VD(V) 20 15 10 5 0
0
1
2
3
4
5
6
7
8
9
10 (s)
Switching Waveform at Constant Current Mode (16.8 V setting at 10 V)
OUT(V) 15 VAC = 19 V CC mode IBATT = 3 A setting VBATT = 10 V 10 5 0
VD(V) 20 15 10 5 0
0
1
2
3
4
5
6
7
8
9
10 (s)
(Continued)
39
MB39A113
Soft-start Operating Waveform at Constant Voltage Mode (12.6 V setting) (1)
VAC = 19 V CV mode RL = 20 VBATT = 12.6 V setting
VO(V) 20 15 10 5 VO 0 CTL(V) 5 CTL 0
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
Soft-start Operating Waveform at Constant Voltage Mode (12.6 V setting) (2)
CVM(V) 6 4 2 CVM 0 OVP(V) 5 OVP 0 CTL(V) 5 CTL 0 VAC = 19 V CV mode RL = 20 VBATT = 12.6 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
(Continued)
40
MB39A113
Discharge Operating Waveform at Constant Voltage Mode (12.6 V setting) (1)
VAC = 19 V CV mode RL = 20 VBATT = 12.6 V setting
VO(V) 20 15 10 5 VO 0 CTL(V) 5 CTL 0
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
Discharge Operating Waveform at Constant Voltage Mode (12.6 V setting) (2)
CVM(V) 6 4 2 CVM 0 OVP(V) 5 0 CTL(V) 5 CTL 0 OVP VAC = 19 V CV mode RL = 20 VBATT = 12.6 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
(Continued)
41
MB39A113
Soft-start Operating Waveform at Constant Current Mode (12.6 V setting) (1)
VO(V) 20 15 10 5 VO 0 CTL(V) 5 CTL 0 VAC = 19 V CC mode RL = 3.33 VBATT = 12.6 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
Soft-start Operating Waveform at Constant Current Mode (12.6 V setting) (2)
CVM(V) 6 4 2 CVM 0 OVP(V) 5 OVP 0 CTL(V) 5 CTL 0 VAC = 19 V CC mode RL = 3.33 VBATT = 12.6 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
(Continued)
42
MB39A113
Discharge Operating Waveform at Constant Current Mode (12.6 V setting) (1)
VO(V) 20 15 10 5 VO 0 CTL(V) 5 CTL 0 VAC = 19 V CC mode RL = 3.33 VBATT = 12.6 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
Discharge Operating Waveform at Constant Current Mode (12.6 V setting) (2)
CVM(V) 6 4 2 CVM 0 OVP(V) 5 0 CTL(V) 5 CTL 0 OVP VAC = 19 V CC mode RL = 3.33 VBATT = 12.6 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
(Continued)
43
MB39A113
Soft-start Operating Waveform at Constant Voltage Mode (16.8 V setting) (1)
VAC = 19 V CV mode RL = 20 VBATT = 16.8 V setting
VO(V) 20 15 10 5 VO 0 CTL(V) 5 CTL 0
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
Soft-start Operating Waveform at Constant Voltage Mode (16.8 V setting) (2)
CVM(V) 6 4 2 CVM 0 OVP(V) 5 OVP 0 CTL(V) 5 CTL 0 VAC = 19 V CV mode RL = 20 VBATT = 16.8 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
(Continued)
44
MB39A113
Discharge Operating Waveform at Constant Voltage Mode (16.8 V setting) (1)
VO(V) 20 15 10 5 VO 0 CTL(V) 5 CTL 0 VAC = 19 V CV mode RL = 20 VBATT = 16.8 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
Discharge Operating Waveform at Constant Voltage Mode (16.8 V setting) (2)
CVM(V) 6 4 2 CVM 0 OVP(V) 5 OVP 0 CTL(V) 5 CTL 0 VAC = 19 V CV mode RL = 20 VBATT = 16.8 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
(Continued)
45
MB39A113
Soft-start Operating Waveform at Constant Current Mode (16.8 V setting) (1)
VO(V) 20 15 10 5 VO 0 CTL(V) 5 CTL 0 VAC = 19 V CC mode RL = 3.33 VBATT = 16.8 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
Soft-start Operating Waveform at Constant Current Mode (16.8 V setting) (2)
CVM(V) 6 4 2 CVM 0 OVP(V) 5 OVP 0 CTL(V) 5 CTL 0 VAC = 19 V CC mode RL = 3.33 VBATT = 16.8 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
(Continued)
46
MB39A113
(Continued)
Discharge Operating Waveform at Constant Current Mode (16.8 V setting) (1)
VO(V) 20 15 10 5 VO 0 CTL(V) 5 CTL 0 VAC = 19 V CC mode RL = 3.33 VBATT = 16.8 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
Discharge Operating Waveform at Constant Current Mode (16.8 V setting) (2)
CVM(V) 6 4 2 CVM 0 OVP(V) 5 OVP 0 CTL(V) 5 CTL 0 VAC = 19 V CC mode RL = 3.33 VBATT = 16.8 V setting
0
2.5
5.0
7.5
10.0
12.5
15.0
17.5
20.0
22.5
25.0 (ms)
47
MB39A113
s NOTES ON USE
* Take account of common impedance when designing the earth line on a printed wiring board. * Take measures against static electricity. * * * * For semiconductors, use antistatic or conductive containers. When storing or carrying a printed circuit board after chip mounting, put it in a conductive bag or container. The work table, tools, and measuring instruments must be grounded. The worker must put on a grounding device containing 250 k to 1 M resistors in series.
* Do not apply a negative voltage. * Applying a negative voltage of -0.3 V or less to an LSI may generate a parasitic transistor, resulting in malfunction.
48
MB39A113
s ORDERING INFORMATION
Part number MB39A113PFV Package 24-pin plastic SSOP (FPT-24P-M03) Remarks
49
MB39A113
s PACKAGE DIMENSION
24-pin plastic SSOP (FPT-24P-M03) Note 1) *1 : Resin protrusion. (Each side : +0.15 (.006) Max) . Note 2) *2 : These dimensions do not include resin protrusion. Note 3) Pins width and pins thickness include plating thickness. Note 4) Pins width do not include tie bar cutting remainder.
0.170.03 (.007.001)
13
*17.750.10(.305.004)
24
*2 5.600.10
INDEX
7.600.20 (.220.004) (.299.008) Details of "A" part 1.25 -0.10 .049 -.004
+0.20 +.008
(Mounting height)
0.25(.010) 0~8
1
12
"A"
M
0.65(.026)
0.24 -0.07 .009 -.003
+0.08 +.003
0.13(.005)
0.500.20 (.020.008) 0.600.15 (.024.006)
0.100.10 (.004.004) (Stand off)
0.10(.004)
C
2003 FUJITSU LIMITED F24018S-c-4-5
Dimensions in mm (inches) . Note : The values in parentheses are reference values.
50
MB39A113
FUJITSU LIMITED
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F0405 (c) FUJITSU LIMITED Printed in Japan
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